Method for recovering data transmitted over a plurality of channels employing wireless code division multiple access communication

ABSTRACT

A method for recovering data transmitted over a plurality of channels employing wireless code division multiple access communication, comprises receiving the plurality of channels as a received signal, each channel associated with a code. Others from the plurality of channels from the received signal is subtracted for each for each of the plurality of channels and a result a result of that subtracting as data for that channel is despread. That channel despread signal is respread with a respective channel code, wherein the respreading channel code is aligned to a timing of the despread received signal.

CROSS REFERENCE TO RELATED APPLICATIONS

This application is a continuation of application Ser. No. 10/201,797,filed on Jul. 24, 2002, which is a continuation of application Ser. No.09/851,740, filed May 9, 2001, now U.S. Pat. No. 6,868,076, which is acontinuation of application Ser. No. 09/276,019, filed Mar. 25, 1999,now U.S. Pat. No. 6,259,688, which is a continuation of U.S. applicationSer. No. 08/939,146, filed Sep. 29, 1997, now U.S. Pat. No. 6,014,373,which is a continuation of U.S. application Ser. No. 08/654,994, filedMay 29, 1996, now U.S. Pat. No. 5,719,852, which is a continuation ofU.S. application Ser. No. 08/279,477, filed Jul. 26, 1994, now U.S. Pat.No. 5,553,062, which is a continuation-in-part of U.S. application Ser.No. 08/051,017, filed Apr. 22, 1993, now U.S. Pat. No. 5,363,403, all ofwhich are incorporated herein by reference as if fully set forth.

BACKGROUND

This invention relates to spread-spectrum communications, and moreparticularly to an interference canceller employed by a remote terminalfor reducing interference in a direct sequence, code division multipleaccess receiver.

Direct sequence, code division multiple access, spread-spectrumcommunications systems are capacity limited by interference caused byother simultaneous users. This is compounded if adaptive power controlis not used, or is used but is not perfect.

Code division multiple access is interference limited. The more userstransmitting simultaneously, the higher the bit error rate (BER).Increased capacity requires forward error correction (FEC) coding, whichin turn, increases the data rate and limits capacity.

SUMMARY

A general object of the invention is to reduce noise resulting from N−1interfering signals in a direct sequence, spread-spectrum code divisionmultiple access receiver.

The present invention, as embodied and broadly described herein,provides a method for recovering data transmitted over a plurality ofchannels employing wireless code division multiple access communication.The method comprises receiving the plurality of channels as a receivedsignal, each channel associated with a code. Others from the pluralityof channels from the received signal is subtracted for each for each ofthe plurality of channels and a result a result of that subtracting asdata for that channel is despread. That channel despread signal isrespread with a respective channel code, wherein the respreading channelcode is aligned to a timing of the despread received signal.

Additional objects and advantages of the invention are set forth in partin the description which follows, and in part are obvious from thedescription, or may be learned by practice of the invention. The objectsand advantages of the invention also may be realized and attained bymeans of the instrumentalities and combinations particularly pointed outin the appended claims.

BRIEF DESCRIPTION OF THE DRAWING(S)

The accompanying drawings, which are incorporated in and constitute apart of the specification, illustrate preferred embodiments of theinvention, and together with the description serve to explain theprinciples of the invention.

FIG. 1 is a block diagram of the spread-spectrum CDMA interferencecanceller using correlators;

FIG. 2 is a block diagram of the spread-spectrum CDMA interferencecanceller for processing multiple channels using correlators;

FIG. 3 is a block diagram of the spread-spectrum CDMA interferencecanceller using matched filters;

FIG. 4 is a block diagram of the spread-spectrum CDMA interferencecanceller for processing multiple channels using matched filters;

FIG. 5 is a block diagram of the spread-spectrum CDMA interferencecanceller having multiple iterations for processing multiple channels;

FIG. 6 illustrates theoretical performance characteristic for E_(b)/η=6dB;

FIG. 7 illustrates theoretical performance characteristic for E_(b)/η=10dB;

FIG. 8 illustrates theoretical performance characteristic for E_(b)/η=15dB;

FIG. 9 illustrates theoretical performance characteristic for E_(b)/η=20dB;

FIG. 10 illustrates theoretical performance characteristic forE_(b)/η=25 dB;

FIG. 11 illustrates theoretical performance characteristic forE_(b)/η=30 dB;

FIG. 12 is a block diagram of interference cancellers connectedtogether;

FIG. 13 is a block diagram combining the outputs of the interferencecancellers of FIG. 12;

FIG. 14 illustrates simulation performance characteristics forasynchronous, PG=100, Equal Powers, E_(b)N=30 dB;

FIG. 15 illustrates simulation performance characteristics forasynchronous, PG=100, Equal Powers, E_(b)N=30 dB;

FIG. 16 illustrates simulation performance characteristics forasynchronous, PG=100, Equal Powers, E_(b)N=30 dB; and

FIG. 17 illustrates simulation performance characteristics forasynchronous, PG=100, Equal Powers, E_(b)N=30 db.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT(S)

Reference now is made in detail to the present preferred embodiments ofthe invention, examples of which are illustrated in the accompanyingdrawings, wherein like reference numerals indicate like elementsthroughout the several views.

In the exemplary arrangement shown in FIG. 1, a spread-spectrum codedivision multiple access (CDMA) interference canceller is provided forreducing interference in a spread-spectrum CDMA receiver having Nchannels. The present invention also works on a spread-spectrum codedivision multiplexed (CDMA) system. Accordingly, without loss ofgenerality, the term spread-spectrum CDMA signal, as used herein,includes spread-spectrum CDMA signals and spread-spectrum CDM signals.In a personal communications service, the interference canceller may beused at a base station or in a remote unit such as a handset.

FIG. 1 illustrates the interference canceller for the first channel,defined by the first chip-code signal. The interference cancellerincludes a plurality of despreading means, a plurality of timing means,a plurality of spread-spectrum-processing means, subtracting means, andfirst channel-despreading means.

Using a plurality of chip-code signals, the plurality of despreadingmeans despreads the received spread-spectrum CDMA signals as a pluralityof despread signals, respectively. In FIG. 1 the plurality ofdespreading means is shown as first despreading means, seconddespreading means, through N^(th) despreading means. The firstdespreading means includes a first correlator, which is embodied, by wayof example, as a first mixer 51, first chip-code-signal generator 52,and a first integrator 54. The first integrator 54 alternatively may bea first lowpass filter or a first bandpass filter. The first mixer 51 iscoupled between the input 41 and the first chip-code-signal generator 52and the first integrator 54.

The second despreading means includes a second correlator, which isembodied, by way of example, as second mixer 61, second chip-code-signalgenerator 62 and second integrator 64. The second integrator 64alternatively may be a second lowpass filter or a second bandpassfilter. The second mixer 61, is coupled between the input 41, the secondchip-code-signal generator 62, and the second integrator 64.

The N^(th) despreading means is depicted as an N^(th) correlator shown,by way of example, as N^(th) mixer 71, and N^(th) chip-code-signalgenerator 72, and N^(th) integrator 74. The N^(th) integrator 74alternatively may be an N^(th) lowpass filter or an N^(th) bandpassfilter. The N^(th) mixer 71 is coupled between the input 41, the N^(th)chip-code-signal generator 72 and the N^(th) integrator 74.

As is well known in the art, the first through N^(th) despreading meansmay be embodied as any device which can despread a channel in aspread-spectrum signal.

The plurality of timing means may be embodied as a plurality of delaydevices 53, 63, 73. A first delay device 53 has a delay time T, which isapproximately the same as the integration time T_(b) of first integrator54, or time constant of the first lowpass filter or first bandpassfilter. A second delay device 63 has a time delay T, which isapproximately the same as the integration time T_(b) of secondintegrator 64, or time constant of the second lowpass filter or secondbandpass filter. Similarly, the N^(th) delay device 73 has a time delayT, which is approximately the same as the integration time T_(b) ofN^(th) integrator 74, or time constant of the N^(th) lowpass filter orN^(th) bandpass filter. Typically, the integration times of the firstintegrator 54, second integrator 64 through N^(th) integrator 74 are thesame. If lowpass filters are used, then typically the time constants ofthe first lowpass filter, second lowpass filter through N^(th) lowpassfilter are the same. If bandpass filters are used, then the timeconstants of the first bandpass filter, second bandpass filter throughN^(th) bandpass filter are the same.

The plurality of spread-spectrum-processing means regenerators each ofthe plurality of despread signals as a plurality of spread-spectrumsignals. The plurality of spread-spectrum-processing means uses a timedversion, i.e. delayed version, of the plurality of chip-code signals,for spread-spectrum processing the plurality of despread signals,respectively, with a chip-code signal corresponding to a respectivedespread signal. The plurality of spread-spectrum-processing means isshown, by way of example, as a first processing mixer 55, a secondprocessing mixer 65, through an N^(th) processing mixer 75. The firstprocessing mixer 55 is coupled to the first integrator 54, and through afirst delay device 53 to the first chip-code-signal generator 52. Thesecond processing mixer 65 is coupled to the second integrator 64, andthrough the second delay device 63 to the second chip-code-signalgenerator 62. The N^(th) processing mixer 75 is coupled to the N^(th)integrator 74 through the delay device 73 to the N^(th) chip-code-signalgenerator 72.

For reducing interference to a channel using an i^(th) chip-code signalof the spread-spectrum CDMA signal, the subtracting means subtracts,from the spread-spectrum CDMA signal, each of the N−1spread-spectrum-processed-despread signals not corresponding to thei^(th) channel. The subtracting means thereby generates a subtractedsignal. The subtracting means is shown as a first subtractor 150. Thefirst subtractor 150 is shown coupled to the output of the secondprocessing mixer 65, through the N^(th) processing mixer 75.Additionally, the first subtractor 150 is coupled through a main delaydevice 48 to the input 41.

The i^(th) channel-despreading means despreads the subtracted signalwith the i^(th) chip-code signal as the i^(th) channel. The firstchannel-despreading means is shown as a first channel mixer 147. Thefirst channel mixer 147 is coupled to the first delay device 53, and tothe first subtractor 150. The first channel integrator 146 is coupled tothe first channel mixer 147.

The first chip-code-signal generator 52, the second chip-code-signalgenerator 62, through the N^(th) chip-code signal generator 72 generatea first chip-code signal, a second chip-code signal, through an N^(th)chip-code signal, respectively. The term “chip-code signal” is usedherein to mean the spreading signal of a spread-spectrum signal, as iswell known in the art. Typically the chip-code signal is generated froma pseudorandom (PN) sequence. The first chip-code signal, the secondchip code signal, through the N^(th) chip-code signal might be generatedfrom a first PN sequence, a second PN sequence, through an N^(th) PNsequence, respectively. The first PN sequence is defined by or generatedfrom a first chip codeword, the second PN sequence is defined by orgenerated from a second chip codeword, through the N^(th) PN sequence isdefined by or generated from an N^(th) chip-codeword. Each of the firstchip codeword, second chip codeword through N^(th) chip codeword isdistinct, i.e. different from one another. In general, a chip codewordcan be the actual sequence of a PN sequence, or used to define settingsfor generating the PN sequence. The settings might be the delay taps ofshift registers, for example.

A first channel of a received spread-spectrum CDMA signal at input 41 isdespread by first mixer 51 as a first despread signal, using the firstchip-code signal generated by first chip-code-signal generator 52. Thefirst despread signal from the first mixer 51 is filtered through firstintegrator 54. First integrator 54 integrates for a time T_(b), the timeduration of a symbol such as a bit. At the same time, the firstchip-code signal is delayed by time T by delay device 53. The delay timeT is approximately equal to the integration time T_(b) plus system orcomponent delays. Systems or component delays are usually small,compared to integration time T_(b).

The delayed version of the first chip-code signal is processed with thefirst despread signal from the output of the first integrator 54 usingthe first spreading mixer 55. The output of the first spreading mixer 55is fed to subtractors other than first subtractor 150 for processing thesecond through N^(th) channels of the spread-spectrum CDMA signal.

For reducing interference to the first channel of the spread-spectrumCDMA signal, the received spread-spectrum CDMA signal is processed bythe second through N^(th) despreaders as follows. The second channel ofthe spread-spectrum CDMA signal is despread by the second despreadingmeans. At the second mixer 61, a second chip-code signal, generated bythe second chip-code-signal generator 62, despreads the second channelof the spread-spectrum CDMA signal. The despread second channel isfiltered through second integrator 64. The output of the secondintegrator 64 is the second despread signal. The second despread signalis spread-spectrum processed by second processing mixer 65 by a delayedversion of the second chip-code signal. The second chip-code signal isdelayed through delay device 63. The delay device 63 delays the secondchip-code signal by time T. The second channel mixer 65 spread-spectrumprocesses a timed version, i.e. delayed version, of the second chip-codesignal with the filtered version of the second spread-spectrum channelfrom second integrator 64. The term “spread-spectrum process” as usedherein includes any method for generating a spread-spectrum signal bymixing or modulating a signal with a chip-code signal. Spread-spectrumprocessing may be done by product devices, EXCLUSIVE-OR gates, matchedfilters, or any other device or circuit as is well known in the art.

Similarly, the N^(th) channel of the spread-spectrum CDMA signal isdespread by the N^(th) despreading means. Accordingly, the receivedspread-spectrum CDMA signal has the N^(th) channel despread by N^(th)mixer 61, by mixing the spread-spectrum CDMA signal with the N^(th)chip-code signal from N^(th) chip-code-signal generator 72. The outputof the N^(th) mixer 71 is filtered by N^(th) integrator 74. The outputof the N^(th) integrator 74, which is the N^(th) despread signal, is adespread and filtered version of the N^(th) channel of thespread-spectrum CDMA signal. The N^(th) despread signal isspread-spectrum processed by a delayed version of the N^(th) chip-codesignal. The N^(th) chip-code signal is delayed through N^(th) delaydevice 73. The N^(th) processing mixer 75 spread-spectrum processes thetimed version, i.e. a delayed version, of the N^(th) chip-code signalwith the N^(th) despread signal.

At the first subtractor 150, each of the outputs of the secondprocessing mixer 65 through the N^(th) processing mixer 75 is subtractedfrom a timed version, i.e. a delayed version, of the spread-spectrumCDMA signal from input 41. The delay of the spread-spectrum CDMA signalis timed through the first main delay device 48. Typically, the delay ofthe first main delay device 48 is time T, which is approximately equalto the integration time of the first integrator 54 through N^(th)integrator 74.

At the output of the first subtractor 150, is generated a firstsubtracted signal. The first subtracted signal, for the first channel ofthe spread-spectrum CDMA signal, is defined herein to be the outputsfrom the second processing mixer 65 through N^(th) processing mixer 75,subtracted from the delayed version of the spread-spectrum CDMA signal.The second subtracted signal through N^(th) subtracted signal aresimilarly defined.

The delayed version of the first chip-code signal from the output offirst delay device 53 is used to despread the output of the firstsubtractor 150. Accordingly, the first subtracted signal is despread bythe first chip-code signal by first channel mixer 147. The output of thefirst channel mixer 147 is filtered by first channel integrator 147.This produces an output estimate d₁ of the first channel of thespread-spectrum CDMA signal.

As illustratively shown in FIG. 2, a plurality of subtractors 150, 250,350, 450 can be coupled appropriately to the input 41 and to a firstspreading mixer 55, second spreading mixer 65, third spreading mixer,through an N^(th) spreading mixer 75 of FIG. 1. The plurality ofsubtractors 150, 250, 350, 450 also are coupled to the main delay device48 from the input 41. This arrangement can generate a first subtractedsignal from the first subtractor 150, a second subtracted signal fromthe second subtractor 250, a third subtracted signal from the thirdsubtractor 350, through an N^(th) subtracted signal from an N^(th)subtractor 450.

The outputs of the first subtractor 150, second subtractor 250, thirdsubtractor 350, through the N^(th) subtractor 450 are each coupled to arespective first channel mixer 147, second channel mixer 247, thirdchannel mixer 347, through N^(th) channel mixer 447. Each of the channelmixers is coupled to a delayed version of the first chip-code signal, g₁(t-T), second chip-code signal, g₂ (t-T), third chip-code signal, g₃(t-T), through N^(th) chip-code signal, g_(N) (t-T). The outputs of eachof the respective first channel mixer 147, second channel mixer 247,third channel mixer 347, through N^(th) channel mixer 447 are coupled toa first channel integrator 146, second channel integrator 246, thirdchannel integrator 346 through N^(th) channel integrator 446,respectively. At the output of each of the channel integrators isproduced an estimate of the respective first channel d₁, second channeld₂, third channel d₃, through N^(th) channel d_(N).

Referring to FIG. 1, use of the present invention is illustrated for thefirst channel of the spread-spectrum CDMA signal, with the understandingthat the second through N^(th) CDMA channels work similarly. A receivedspread-spectrum CDMA signal at input 41 is delayed by delay device 48and fed to the first subtractor 150. The spread-spectrum CDMA signal hasthe second channel through N^(th) channel despread by second mixer 61using the second chip-code signal, through the N^(th) mixer 71 using theN^(th) chip-code signal. The respective second chip-code signal throughthe N^(th) chip-code signal are generated by the second chip-code-signalgenerator 62 through the N^(th) chip-code-signal generator 72. Thesecond channel through N^(th) channel are despread and filtered throughthe second integrator 64 through the N^(th) integrator 74, respectively.The despreading removes, partially or totally, the non-despread channelsat the outputs of each of the second integrator 64 through N^(th)integrator 74.

In a preferred embodiment, each of the chip-code signal used for thefirst chip-code-signal generator 52, second chip-code-signal generator62 through the N^(th) chip-code-signal generator 72, are orthogonal toeach other. Use of chip-code signals having orthogonality however, isnot required for operation of the present invention. When usingorthogonal chip-code signals, the despread signals have the respectivechannel plus noise at the output of each of the integrators. Withorthogonal chip-code signals, theoretically the mixers remove channelsorthogonal to the despread channel. The respective channel isspread-spectrum processed by the respective processing mixer.

At the output of the second processing mixer 65 through the N^(th)processing mixer 75 is a respread version of the second channel throughthe N^(th) channel, plus noise components contained therein. Each of thesecond channel through N^(th) channel is then subtracted from thereceived spread-spectrum CDMA signal by the first subtractor 150. Thefirst subtractor 150 produces the first subtracted signal. The firstsubtracted signal is despread by a delayed version of the firstchip-code signal by first channel mixer 147, and filtered by firstchannel filter 146. Accordingly, prior to despreading the first channelof the spread-spectrum CDMA signal, the second through N^(th) channelsplus noise components aligned with these channels are subtracted fromthe received spread-spectrum CDMA signal. As illustratively shown inFIG. 3, an alternative embodiment of the spread-spectrum CDMAinterference canceller includes a plurality of first despreading means,a plurality of spread-spectrum-processing means, subtracting means, andsecond despreading means. In FIG. 3, the plurality of despreading meansis shown as first despreading means, second despreading means throughN^(th) despreading means. The first despreading means is embodied as afirst matched filter 154. The first matched filter 154 has an impulseresponse matched to the first chip-code signal, which is used tospread-spectrum process and define the first channel of thespread-spectrum CDMA signal. The first matched filter 154 is coupled tothe input 41.

The second despreading means is shown as second matched filter 164. Thesecond matched filter 164 has an impulse response matched to the secondchip-code signal, which is used to spread-spectrum process and definethe second channel of the spread-spectrum CDMA signal. The secondmatched filter 164 is coupled to the input 41.

The N^(th) despreading means is shown as an N^(th) matched filter 174.The N^(th) matched filter has an impulse response matched to the N^(th)chip-code signal, which is used to spread-spectrum process and definethe N^(th) channel of the spread-spectrum CDMA signal. The N^(th)matched filter is coupled to the input 41.

The term matched filter, as used herein, includes any type of matchedfilter that can be matched to a chip-code signal. The matched filter maybe a digital matched filter or analog matched filter. A surface acousticwave (SAW) device may be used at a radio frequency (RF) or intermediatefrequency (IF). Digital signal processors and application specificintegrated circuits (ASIC) having matched filters may be used at RF, IFor baseband frequency.

In FIG. 3, the plurality of spread-spectrum-processing means is shown asthe first processing mixer 55, the second processing mixer 65, throughthe N^(th) processing mixer 75. The first processing mixer 55 may becoupled through a first adjustment device 97 to the firstchip-code-signal generator 52. The second processing mixer 65 may becoupled through the second adjustment device 98 to the secondchip-code-signal generator 62. The N^(th) processing mixer 75 may becoupled through the N^(th) adjustment device 99 to the N^(th)chip-code-signal generator 72. The first adjusting device 97, secondadjustment device 98 through N^(th) adjustment device 99 are optional,and are used as an adjustment for aligning the first chip-code signal,second chip-code signal through N^(th) chip-code signal with the firstdespread signal, second despread signal through N^(th) despread signal,outputted from the first matched filter 154, second matched filter 164through N^(th) matched filter 174, respectively.

The subtracting means is shown as the first subtractor 150. The firstsubtractor 150 is coupled to the output of the second processing mixer65, through the N^(th) processing mixer 75. Additionally, the firstsubtractor 150 is coupled through the main delay device 48 to the input41.

The first channel-despreading means is shown as a first channel-matchedfilter 126. The first channel-matched filter 126 is coupled to the firstsubtractor 150. The first channel-matched filter 126 has an impulseresponse matched to the first chip-code signal.

A first channel of a received spread-spectrum CDMA signal, at input 41,is despread by first matched filter 154. The first matched filter 154has an impulse response matched to the first chip-code signal. The firstchip-code signal defines the first channel of the spread-spectrum CDMAsignal, and is used by the first chip-code-signal generator 52. Thefirst chip-code signal may be delayed by adjustment time τ by adjustmentdevice 97. The output of the first matched filter 154 is spread-spectrumprocessed by the first processing mixer 55 with the first chip-codesignal. The output of the first processing mixer 55 is fed tosubtractors other than the first subtractor 150 for processing thesecond channel through the N^(th) channel of the spread-spectrum CDMAsignals.

For reducing interference to the first spread-spectrum channel, thereceived spread-spectrum CDMA signal is processed by the seconddespreading means through N^(th) despreading means as follows. Thesecond matched filter 164 has an impulse response matched to the secondchip-code signal. The second chip-code signal defines the second channelof the spread-spectrum CDMA signal, and is used by the secondchip-code-signal generator 62. The second matched filter 164 despreadsthe second channel of the spread-spectrum CDMA signal. The output of thesecond matched filter 164 is the second despread signal. The seconddespread signal triggers second chip-code-signal generator 62. Thesecond despread signal also is spread-spectrum processed by secondprocessing mixer 65 by a timed version of the second chip-code signal.The timing of the second chip-code signal triggers the second despreadsignal from the second matched filter 164.

Similarly, the N^(th) channel of the spread-spectrum CDMA signal isdespread by the N^(th) despreading means. Accordingly, the receivedspread-spectrum CDMA signal has the N^(th) channel despread by N^(th)matched filter 174. The output of the N^(th) matched filter 174 is theN^(th) despread signal, i.e. a despread and filtered version of theN^(th) channel of the spread-spectrum CDMA signal. The N^(th) despreadsignal is spread-spectrum processed by a timed version of the N^(th)chip-code signal. The timing of the N^(th) chip-code signal is triggeredby the N^(th) despread signal from the N^(th) matched filter 174. TheN^(th) processing mixer 75 spread-spectrum processes the timed versionof the N^(th) chip-code signal with the N^(th) despread signal.

At the first subtractor 150, each of the outputs of the secondprocessing mixer 65 through the N^(th) processing mixer 75 aresubtracted from a delayed version of the spread-spectrum CDMA signalfrom input 41. The delay of the spread-spectrum CDMA signal is timedthrough delay device 48. The time of delay device 48 is set to align thesecond through N^(th) spread-spectrum-processed-despread signals forsubtraction from the spread-spectrum CDMA signal. This generates at theoutput of the first subtractor 150, a first subtracted signal. Thesubtracted signal is despread by the first channel-matched filter 126.This produces an output estimate d₁ of the first channel of thespread-spectrum CDMA signal.

As illustrated in FIG. 4, a plurality of subtractors 150, 250, 350, 450can be coupled appropriately to the output from a first processingmixer, second processing mixer, third processing mixer, through anN^(th) processing mixer, and to a main delay device form the input. Afirst subtracted signal is outputted from the first subtractor 150, asecond subtracted signal is outputted from the second subtractor 250, athird subtracted signal is outputted from the third subtractor 350,through an N^(th) subtractor signal is outputted from the N^(th)subtractor 450.

The output of the first subtractor 150, second subtractor 250, thirdsubtractor 350, through the N^(th) subtractor 450 are each coupled to arespective first channel-matched filter 126, second channel-matchedfilter 226, third channel-matched filter 326, through N^(th)channel-matched filter 426. The first channel-matched filter 126, secondchannel-matched filter 226, third channel-matched filter 326 throughN^(th) channel-matched filter 426 have an impulse response matched tothe first chip-code signal, second chip-code signal, third chip-codesignal, through N^(th) chip-code signal, defining the first channel,second channel, third channel through N^(th) channel, respectively, ofthe spread-spectrum CDMA signal. At each of the outputs of therespective first channel-matched filter 126, second channel-matchedfilter 226, third channel-matched filter 326, through N^(th)channel-matched filter 426, is produced an estimate of the respectivefirst channel d₁, second channel d₂, third channel d₃, through N^(th)channel d_(N).

In use, the present invention is illustrated for the first channel ofthe spread-spectrum CDMA signal, with the understanding that the secondchannel through N^(th) channel work similarly. A receivedspread-spectrum CDMA signal at input 41 is delayed by delay device 48and fed to subtractor 150. The same spread-spectrum CDMA signal has thesecond through N^(th) channel despread by the second matched filter 164through the N^(th) matched filter 174. This despreading removes theother CDMA channels from the respective despread channel. In a preferredembodiment, each of the chip-code signals used for the first channel,second channel, through the N^(th) channel, is orthogonal to the otherchip-code signals. At the output of the first matched filter 154, secondmatched filter 164 through N^(th) matched filter 174, are the firstdespread signal, second despread signal through N^(th) despread signal,plus noise.

The respective channel is spread-spectrum processed by the processingmixers. Accordingly, at the output of the second processing mixer 65through the N^(th) processing mixer 75 is a spread version of the seconddespread signal through the N^(th) despread signal, plus noisecomponents contained therein. Each of thespread-spectrum-processed-despread signals, is then subtracted from thereceived spread-spectrum CDMA signal by the first subtractor 150. Thisproduces the first subtracted signal.

The first subtracted signal is despread by first channel-matched filter126. Accordingly, prior to despreading the first channel of thespread-spectrum CDMA signal, the second channel through N^(th) channelplus noise components aligned with these channels, are subtracted fromthe received spread-spectrum CDMA signal.

As is well known in the art, correlators and matched filters may beinterchanged to accomplish the same function. FIGS. 1 and 3 showalternate embodiments using correlators or matched filters. Thearrangements may be varied. For example, the plurality of despreadingmeans may be embodied as a plurality of matched filters, while thechannel despreading means may be embodied as a correlator.Alternatively, the plurality of despreading means may be a combinationof matched filters and correlators. Also, the spread-spectrum-processingmeans may be embodied as a matched filter or SAW, or as EXCLUSIVE-ORgates or other devices for mixing a despread signal with a chip-codesignal. As is well known in the art, any spread-spectrum despreader ordemodulator may despread the spread-spectrum CDMA signal. The particularcircuits shown in FIGS. 1-4 illustrate the invention by way of example.

The concepts taught in FIGS. 1-4 may be repeated, as shown in FIG. 5.FIG. 5 illustrates a first plurality of interference cancellers 511,512, 513, a second plurality of interference cancellers 521, 522, 523,through an N^(th) plurality of interference cancellers 531, 532, 533.Each plurality of interference cancellers includes appropriate elementsas already disclosed, and referring to FIGS. 1-4, the input is delayedthrough a delay device in each interference canceller.

The received spread-spectrum CDMA signals has interference canceledinitially by the first plurality of interference cancellers 511, 512,513, thereby producing a first set of estimates, i.e. a first estimated₁₁, a second estimate d₁₂, through an N^(th) estimate d_(1N), of thefirst channel, second channel through the N^(th) channel, of thespread-spectrum CDMA signal. The first set of estimates can haveinterference canceled by the second plurality of interference cancellers521, 522, 523. The first set of estimates d₁₁, d₁₂, . . . , d_(1N), ofthe first channel, second channel through N^(th) channel, are input tothe second plurality of interference cancellers, interference canceller521, interference canceller 522 through N^(th) interference canceller523 of the second plurality of interference cancellers. The secondplurality of interference cancellers thereby produce a second set ofestimates, i.e. d₂₁, d₂₂, . . . , d_(2N), of the first channel, secondchannel, through N^(th) channel. Similarly, the second set estimates canpass through a third plurality of interference cancellers, andultimately through an M^(th) set of interference cancellers 531, 532,533, respectively.

The present invention also includes a method for reducing interferencein a spread-spectrum CDMA receiver having N chip-code channels. Each ofthe N channels is identified by a distinct chip-code signal. The methodcomprises the steps of despreading, using a plurality of chip-codesignals, the spread-spectrum CDMA signal as a plurality of despreadsignals, respectively. Using a timed version of the plurality ofchip-code signals, the plurality of despread signals are spread-spectrumprocessed with a chip-code signal corresponding to a respective despreadsignal. Each of the N−1 spread spectrum-processed-despread signals, issubtracted from the spread-spectrum CDMA signal, with the N−1spread-spectrum-processed-despread signals not including aspread-spectrum-processed signal of the i^(th) despread signal, therebygenerating a subtracted signal. The subtracted signal is despread togenerate the i^(th) channel.

The probability of error P_(e) for direct sequence, spread-spectrum CDMAsystem is:$P_{e} = {\frac{1}{2}{{erfc}\left( {\alpha\quad{SNR}} \right)}^{\quad\frac{1}{2}}}$where erfc is complementary error function, SNR is signal-to-noiseratio, and 1≦α≦2. The value of cL depends on how a particularinterference canceller system is designed.

The SNR after interference cancellation and method is given by:${SNR} = \frac{\left( {{PG}/N} \right)^{R + 1}}{1 + {\left( {{PG}/N} \right)^{R + 1}\frac{1}{E_{b}/\eta}\frac{1 - \left( {N/{PG}} \right)^{R + 1}}{1 - {N/{PG}}}}}$where N is the number of channels, PG is the processing gain, R is thenumber of repetitions of the interference canceller, E_(b) is energy perinformation bit and η is noise power spectral density.

FIG. 6 illustrates theoretical performance characteristic, of theinterference canceller and method for when E_(b)/η=6 dB. The performancecharacteristic is illustrated for SNR out of the interference canceller,versus PG/N. The lowest curve, for R=0, is the performance without theinterference canceller. The curves, for R=1 and R=2, illustratesimproved performance for using one and two iterations of theinterference canceller as shown in FIG. 5. As PG/N→1, there isinsufficient SNR to operate. If PG>N, then the output SNR from theinterference canceller approaches E_(b)/η. Further, if (N/PG)^(R+1)<<1,thenSNR→(E_(b)/η)(1−N/PG).

FIG. 7 illustrates the performance characteristic for when E_(b)/η=10dB.

FIG. 7 illustrates that three iterations of the interference cancellercan yield a 4 dB improvement with PG/N=2.

FIG. 8 illustrates the performance characteristic for when E_(b)/η=15dB. With this bit energy to noise ratio, two iterations of theinterference canceller can yield 6 dB improvement for PG/N=2.

FIG. 9 illustrates the performance characteristic for when E_(b)/η=20dB. With this bit energy to noise ratio, two iterations of theinterference canceller can yield 6 dB improvement for PG/N=2. Similarly,FIGS. 10 and 11 show that one iteration of the interference cancellercan yield more than 10 dB improvement for PG/N=2.

The present invention may be extended to a plurality of interferencecancellers. As shown in FIG. 12, a received spread-spectrum signal,R(t), is despread and detected by CDMA/DS detector 611. Each of thechannels is represented as outputs O₀₁, O₀₂, O₀₃, . . . , O_(0m). Thus,each output is a despread, spread-spectrum channel from a receivedspread-spectrum signal, R(t).

Each of the outputs of the CDMA/DS detector 611 is passed through aplurality of interference cancellers 612, 613, . . . , 614, which areserially connected. Each of the spread-spectrum channels passes throughthe interference canceling processes as discussed previously. The inputto each interference canceller is attained by sampling and holding theoutput of the previous stage once per bit time. For channel i, the firstinterference canceller samples the output of the CDMA/DS detector attime t=T+τ_(i). This value is held constant as the input untilt=2T+τ_(i) at which point the next bit value is sample. Thus, the inputwaveforms to the interference canceller are estimates, dˆ_(i)(t−τ_(i)),of the original data waveform (d_(i)(t−τ_(i)), and the outputs aresecond estimates, dˆˆ_(i)(t−τ_(i)). The M spread-spectrum channeloutputs O_(0i), i=1, 2, . . . , M, are passed through interferencecanceller 612 to produce a new corresponding set of channel outputsO_(1i), i=1, 2, . . . , M.

As shown in FIG. 13, the outputs of a particular spread-spectrumchannel, which are at the output of each of the interference cancellers,may be combined. Accordingly, combiner 615 can combine the output of thefirst channel which is from CDMA/DS detector 611, and the output O₁₁from the first interference canceller 612, and the output O₂₁ from thesecond interference canceller 613, through the output O_(N1) from theN^(th) interference canceller 614. Each output to be combined is of thecorresponding bit. Therefore “s” bit time delays is inserted for eachO_(s1). The combined outputs are then passed through the decision device616. This can be done for each spread spectrum channel, and thereforedesignate the outputs of each of the combiners 615, 617, 619 as averagedoutputs O₁ for channel one, averaged output O₂ for channel two, andaveraged output O_(M) for channel M. Each of the averaged outputs aresequentially passed through decision device 616, decision device 618,and decision device 620. Preferably, the averaged outputs havemultiplying factor c_(j) which may vary according to a particulardesign. In a preferred embodiment, c_(j)=½^(j). This allows the outputsof the various interference cancellers to be combined in a particularmanner.

FIGS. 14-17 illustrate simulation performance characteristics for thearrangement of FIGS. 12 and 13. FIGS. 14-17 are for asynchronous channel(relative time delays are uniformly distributed between 0 and bit time,T), processing gain of 100, all users have equal powers, and thermalsignal to noise ratio (E_(b)N of 30 dB). Length 8191 Gold codes are usedfor the PN sequences.

In FIG. 14, performance characteristic of each of the output stages ofFIG. 12 is shown. Thus, S0 represents the BER performance at the outputof CDMA/DS detector 611, S1 represents the BER performance at the outputof interference canceller 612, S2 represents the BER performance at theoutput of interference canceller 613, etc. No combining of the outputsof the interference cancellers are used in determining the performancecharacteristic shown in FIG. 14. Instead, the performance characteristicis for repetitively using interference cancellers. As a guideline, ineach of the subsequent figures the output for each characteristic ofCDMA/DS detector 611 is shown in each figure.

FIG. 15 shows the performance characteristic when the output ofsubsequent interference cancellers are combined. This is shown for aparticular channel. Thus, curve S0 is the output of the CDMA/DS detector611. Curve S1 represents the BER performance of the average of theoutputs of CDMA/DS detector 611 and interference canceller 612. HereC₀=C₁=½C_(j)=0,j not equal to zero, one. Curve S2 represents the BERperformance of the average output of interference canceller 613 andinterference canceller 612. Curve S2 is determined using the combinershown in FIG. 13. Here, C₁ and C₂ are set equal to ½ and all other C_(j)set to zero. Similarly, curve S3 is the performance of the output of asecond and third interference canceller averaged together. Thus, curveS3 is the performance characteristic of the average between outputs of asecond and third interference canceller. Curve S4 is the performancecharacteristic of the average output of a third and fourth interferencecanceller. Only two interference cancellers are taken at a time fordetermining a performance characteristic of an average output of thoseto particular interference cancellers.

FIG. 16 shows the regular outputs for the CDMA/DS detector 611, and afirst and second interference canceller 612, 613. Additionally, theaverage output of the CDMA/DS detector 611 and the first interferencecanceller 612 is shown as S1 AVG. The BER performance of the average ofthe outputs of the first interference canceller 612 and the secondinterference canceller 613 is shown as the average output S2 AVG.

FIG. 17 shows performance characteristic correspondence for those ofFIG. 16, but in terms of signal to-noise ratio in decibels (dB).

It will be apparent to those skilled in the art that variousmodifications can be made to the spread-spectrum CDMA interferencecanceller and method of the instant invention without departing from thescope or spirit of the invention, and it is intended that the presentinvention cover modifications and variations of the spread-spectrum CDMAinterference canceller and method provided they come within the scope ofthe appended claims and their equivalents.

1. A method for recovering data transmitted over a plurality of channelsemploying wireless code division multiple access communication,comprising: a) receiving the plurality of channels as a received signal,each channel associated with a code; b) subtracting for each of theplurality of channels others of the plurality of channels from thereceived signal and despreading a result of that subtracting as data forthat channel; and c) respreading that channel despread signal with arespective channel code; wherein the respreading channel code is alignedto a timing of the despread received signal.
 2. The method of claim 1wherein step (b) includes, for each channel: despreading the receivedsignal with the others channel codes; respreading the despread otherschannel codes using the other channels codes; and subtracting from thereceived signal the respread other channels.
 3. The method of claim 2wherein the despreading is performed by a mixer.
 4. The method of claim2 wherein the despreading is performed by a matched filter.